Analysis and implementation of power management and control strategy for six-phase multilevel ac drive system in fault condition Academic research paper on "Electrical engineering, electronic engineering, information engineering"

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Engineering Science and Technology, an International Journal

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Full Length Article

Analysis and implementation of power management and control strategy for six-phase multilevel ac drive system in fault condition

Sanjeevikumar Padmanabana*, Gabriele Grandib, Frede Blaabjergc, Patrick William Wheelerd, Joseph Olorunfemi Ojoef

a Ohm Technologies, Research & Development, Chennai, Tamil Nadu 600122, India

b Department of Electrical, Electronic, and Information Engineering, Alma Mater Studiorum, University of Bologna, 40136 Bologna, Italy c Department of Energy Technology, Aalborg University, Pontoppidanstraede 101, 9220 Aalborg, Denmark

d Power Electronics, Machines and Control Group, Department of Electrical & Electronics Engineering, Nottingham University, Nottingham NG7 2RD, UK e Center for Energy System Research, Department of Electrical & Computer Engineering, Tennessee Technological University, Cookeville, Tennessee 38505, USA f Eskom Centre of Excellence in HVDC Engineering, University of KwaZulu-Natal, Durban, South Africa

ARTICLE INFO

ABSTRACT

Article history: Received 28 May 2015 Received in revised form 13 July 2015 Accepted 13 July 2015 Available online

Keywords:

Dual three-phase motor Multilevel inverter Multi-phase motor drive Open-end winding Post-fault tolerance Multilevel PWM Level-shifted PWM

This research article exploits the power management algorithm in post-fault conditions for a six-phase (quad) multilevel inverter. The drive circuit consists of four 2-level, three-phase voltage source inverter (VSI) supplying a six-phase open-end windings motor or/impedance load, with circumstantial failure of one VSI investigated. A simplified level-shifted pulse-width modulation (PWM) algorithm is developed to modulate each couple of three-phase VSI as 3-level output voltage generators in normal operation. The total power of the whole ac drive is shared equally among the four isolated DC sources. The developed post-fault algorithm is applied when there is a fault by one VSI and the load is fed from the remaining three healthy VSIs. In faulty conditions the multilevel outputs are reduced from 3-level to 2-level, but still the system propagates with degraded power. Numerical simulation modelling and experimental tests have been carried out with proposed post-fault control algorithm with three-phase open-end (asymmetrical induction motor/R-L impedance) load. A complete set of simulation and experimental results provided in this paper shows close agreement with the developed theoretical background. Copyright © 2015 The Authors. Production and hosting by Elsevier B.V. on behalf of Karabuk University.

This is an open access article under the CC BY-NC-ND license (http://creativecommons.org/licenses/by-nc-nd/4.0/).

1. Introduction

AC power converters are affected by mechanical, thermal, and electrical stresses. These stresses lead to component and system failures [1,2]. Failures include DC-link capacitors, voltage sensors, semiconductor switches and control/gate driver circuits [3-6]. Hence, fault tolerance is mandatory in ac drives power conversion, which ensures fault detection, localization and isolation, allowing continuous propagation [7-10]. Recently, the multi-phase ac machines proved their arrival by the redundancy in configuration, system reliability, and fault tolerance [11-15]. Further, for multiphase ac motor, a minimum of two phases are sufficient to create a rotating field under circumstances when all other phases have failed [11,13].

Multilevel inverters are the prominent alternatives for classical three-phase VSI [16,17], but still the reliability remains lower which is the major drawback [18,19]. Still, the classical three-phase VSI

* Corresponding author. Tel.: +91 9843108228. E-mail address: sanjeevi_12@yahoo.co.in (S. Padmanaban). Peer review under responsibility of Karabuk University.

remains the most reliable choice, hence by properly arranging the multiple VSIs, both multi-phase [20,21] and multilevel configuration can be easily constructed [15,22-24].

A novel ac drive structure for six-phase (asymmetrical) open-end winding asymmetric induction machine is proposed with the capability to generate multilevel outputs [25]. But the PWM strategies are adopted by the complex space vector modulation (SVM) by the nearest three-vector approach to generate multilevel output voltages and complex to implement with real time digital signal processors (dsps). In this research paper, the same ac drive configuration is exploited for the developed post-fault condition with a simplified multi-level (level-shifted PWM) modulation applied to regulate each pair of 2-level VSIs to behave similarly to 3-level outputs. Moreover, the PWM scheme is easy to implement in industrial standard dsp [25,26].

The power circuit consists of four standard 2-level VSIs with four isolated DC sources and hence, the system is absolutely free of zero-sequence components as shown in Fig. 1(a). Equivalent circuit in terms of the three-phase space vectors are shown in Fig. 1(b). Benefit of the topology includes the reduction of construction cost by its conventional structure; high reliability and reduced total harmonic

http://dx.doi.org/10.1016/jjestch.2015.07.007

2215-0986/Copyright © 2015 The Authors. Production and hosting by Elsevier B.V. on behalf of Karabuk University. This is an open access article under the CC BY-NC-ND license (http://creativecommons.org/licenses/by-nc-nd/4.0/).

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distortion (THD) with lower dv/dt at the outputs; and the reduction of stress in the switches. In particular, topology is a viable solution for the applicability of multiphase-phase ac motor/ generator (6-phase, 9-phase, etc.) and renewable energy systems integration for more electric aircraft systems and high-power utilities [12].

Complete ac drive system along the post-fault control strategy algorithm with simplified multilevel PWM scheme is numerically modelled in Matlab/PLECs simulation software. For experimental verifications, the hardware prototype version is implemented with two dsp TMS320F2812 processors and impedance load in open-winding configuration. Set of simulation and experimental results are provided in this paper under different designed testing conditions. Both the simulation and experimental results are always shown in close agreement with developed theoretical background.

This paper is organized as follows: analysis of asymmetrical six-phase open-winding induction motor drive circuit is illustrated in section 2; simplified level-shifted multilevel modulation along with theoretical background and power sharing principles are discussed in section 3; designed post-fault control strategies and predictions are elaborated with theoretical developments in section 4; numerical simulation and experimental implementation results are described with theoretical validation in section 5. Finally, section 6 concludes this research investigation.

2. Analysis of the proposed asymmetrical, six-phase, open-winding induction motor drive

Fig. 1(a) shows the dual three-phase (six-phase asymmetrical) open-winding induction motor fed from four three-phase VSIs with isolated DC sources. Fig. 2(a) correspondingly represents the orthogonal rotating multiple space vectors equivalent circuit [21,27,28]. Complete behavior of the dual three-phase induction machine can be written in stationary reference frames as:

vsi = Rs isi + ~T~<Vsi = Lsi ¡SI + Mi r dt

0 = RRTRi - jpamçRi + ,fRi = Mjsi + Uih dt

vs5 = rsis5 + dd^.Çs 5 = Lsi is5 dt

T = 3pMi is i ■ j ¡ri

Since all DC sources are isolated, it is understood that the proposed system is free of zero-sequence components. Now, the total power P of the ac motor can be written as the sum of power of the two three-phase open-windings P(1)-{1} and P<2)-{2} as [25]:

P (i ) = _ v (i )■ i (i ) 2

P(2)= 3 v(2) ■ i(2) 2

P = P(i) + P(2) = 3K + v(>)■ i(i) + ( + vf) ■ i(2)]

The stator windings voltages v(i) and v(2) are the sum of individual inverter voltages (VS1h(1), VS1l(1) and VS1h(2), VS1l(2)), expressed as:

v(i )= vH > + VU)

vH)+v'2>

There are three degrees of freedom, which allows the total power to be shared equally between the two three-phase open-end windings [25]. By first degree of freedom ki, sharing of power (current) between two three-windings {1} and {2} is predicted as follows:

Fig. 1. (a) Investigated configuration of six-phase (quad) asymmetrical open-end windings ac drive. (b) Equivalent three-phase space vectors circuit. (Healthy state.)

i(i) = 2Ui 7 (2) = 2«i(i - ki ) i

P(i ) = PH )+ P/1 )s kiP P (2) = PH2)+ P[2) = (i - kt )P

By second kv(1) and third kv(2) the degree of freedom that allows the sharing of power (voltages) between the inverters (VS1H(1) and VS1l(1)) and (VS1h(2) and VS1l(2)) of windings {1} and {2} is predicted as follows:

vH ) = k( v(i )

v«1 ) = (- k( ))v(i ) [v]

v (2)-vH -

v(i ) 1 v(2) :

■ ki2>v(2) :( i - kv2>)v(2)

pH > = kv P )

P(i = (- ki' ))P(i) [PfH1-kv2))P(2)

PH2)= k2)P(2)

Hence, the total power can be equally shared among the four VSIs which lead to 25% power demand from each VSI.

3. The PWM modulation strategy for the quad-inverter ac drive system

In order to synthesize the reference voltage vectors v(1) and v(2), proper multilevel PWM algorithm is required to modulate each couple of VSIs and also to satisfy the power sharing between the two windings [29-31], where techniques that suffer by zero-sequence components require compensation in the PWM strategy.

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(a) (b)

(d) (e)

Fig. 2. Space vector representation for VSIs of two three-phase open windings {1} and {2}: (a) Inverter VSIh(1), (b) Inverter VSIl(1), (c) Power sharing between inverter VSIh(1) and VSIl(1). Inverters VSIh(1) and VSIl(1) voltage-level generated space vectors for the three-phase open-end two windings {1} and {2} under (d) healthy state, (e) one inverter faulty state.

An approach followed in Reference 32 provides proper multilevel operation and good power sharing with two VSIs but adopted complex space vector approach. Hence multilevel operation with proper sharing can be easily generated by simplified level-shifted modulation scheme.

The voltage reference vectors v(1) and v(2) corresponds to the output voltages of two three-phase windings given by Eq. 7. By inverse three-phase space vector decomposition approach, the reference voltage space vector of the two windings is determined as [25]:

V (l)= Vslref + Vhrf

V {2)=a-\VsUef + V*5/ef )

Eq. 4 is synthesized using independent three-phase space vectors as shown in Fig. 2(a) and (b) for inverters (VSIH(1), VSIL(1)) and the same applies to inverters (VSIH(2), VSIL(2)). In balanced operation, the sinusoidal voltages space vector vS1/ef determines the voltage limits, with the condition vS3 ref = vS5 ref = 0 leading to the following voltage space vectors for the two sets of open-winding:

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Fig. 4. Post-fault configuration equivalent three-phase space vectors circuit: (a) one failed inverter VS1L(1), vL(1) = 0, and (b) minimization of power loss VS1L(2), vL(2) = 0.

Fig. 3. Level-shifted multilevel modulation scheme for inverters VS1h(1) (normal line) and VS1l(1) (dotted line): (a) modulation signals for the three-phase open-winding {1}, (b) switching pattern.

v<1> = m(1)Vdc cos (G-n) - Vdcl2 v1 = m(1)Vdc cosG- Vdc/2 " ¡v<H) = m(ï)Vdc cos (G - 5n / 6) - VdJ2 ^vp» = m(2)Vdc cos (G + n6) - Vdc/2 "

4. Proposed post-fault tolerant strategy predictions

vw = vS1ref v(2) = a- ■ vS1ref

In Fig. 2(d), regular hexagon gives voltage limitation of each VSI by the space vectors. For sinusoidal balanced voltages operation, the voltage limit is restricted to 2/\[3 Vdc, with the outer circle radius shown in Fig. 2(d). By the symmetry of the triangles, the analysis can be limited to triangle OAB (shaded area) [32]. The sharing principle is shown in Fig. 2(c) for proper power sharing with multilevel waveforms.

Level-shifted pulse width modulation (PWM) is a well known scheme which can be used in all types of multilevel inverters. For /-levels there are (l - 1) carriers shifted by l/(l - 1)Vdc. Fig. 3(a) shows a common single carrier and this carrier is compared with each modulating signals for use in the corresponding part of the multilevel inverter. Implementation of the level-shifted PWM scheme for inverters (VSIH(1), VSIL(1)) is shown in Fig. 3(a) and the corresponding switching pattern is shown in Fig. 3(b) (OCD triangle). The modulation that can be achieved using common triangular carriers with the references of each VSI is given as:

In a multiple ac drive connected system, if fault occurs in one VSI, the concerned faulty unit will be completely isolated from the source as well as from the load by the protective circuits, i.e. bypass switches/circuit breakers for continuous propagation of the system. In this post-fault investigation, if one VSIL(1) predicted faulti-ness, the ac drive continues to operate but the degrees of freedom reduce from three degrees to two degrees and is represented in space vector equivalent circuit given by Fig. 4(a). Now, the open-end windings configuration collapses to three-phase star connected windings, where VSIH(1) alone provides the power in windings {1}. But in windings {2}, where VSIH(2) and VSIL(2) provided the power, the two degrees of freedom are now represented by kv(2) sharing voltage between VSIH(2) and VSIl(2), and k sharing current between two three-phase windings {1} and {2}. Hence, according to Eq. 10 the post-fault propagation is predicted as:

vc> = 0

vH>= v (•)'

By Eq. 9, Eq. 11 and Eq. 15, VSIs individual power can be written

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P > =0 P > = kiP

p[2'> = ( - k )(-Wy)P PH2)=( - k )kWp

Table 1

Simulation parameters of dual three-phase asymmetrical induction motor.

Consequence of this fault will reduce the maximum output voltage by half for the three-phase windings {1} from 2/V3Vdc to 1/V3Vdc, as clearly shown in Fig. 2(e). Overall, there is a 50% decrement in maximum power of the ac drive system. In this circumstance, a different control strategy can be adopted in this postfault operation with available three healthy VSIs (VS1h(1), VS1h(2), and VS1L(2)). Two relevant investigations are developed: the first one concerns power loss minimization and the second one concerns balanced power sharing among the three healthy VS1s (VS1H(1), VS1H(2), and VS1L(2)). For investigation purposes Eq. 15 will be formulated in numerical simulations/experimental test to represent this postfault condition without using any protective circuitries.

4.1. Minimization of power losses

The first post-fault condition is adopted for the balanced sharing of currents between the two windings {1} and {2}, which is ensured by simply applying ki = 1/2. Voltage sharing coefficient kv(2) synthesizes voltage reference v(2) between inverters VS1H(2) and VS1L(2). Subsequently, the usage of inverters (VS1H(2), VS1L(2)) is not optimal from the point of inverter losses. The desired output voltage can be synthesized with just one inverter (VS1H(2) or VS1L(2)), therefore inverter VS1H(1) can propagate with just VS1H(2) and set VS1L(2) to zero voltage output or vice versa, maintaining exactly the same characteristics. Hence, the open-end windings configuration collapses to star connected in both windings {1} and {2}, represented by the space vector equivalent circuit by Fig. 4(b). By Eq. 10 and Eq. 11, prediction for the post-fault condition by Eq. 12 can be further written as:

jv<2> =

>k?=i ,

P >=0 rpp> = 0 ]p— =2p {p?> =2P«ki~2

For investigation purposes Eq. 17 will be formulated in numerical simulations/experimental test to represent this first postfault condition without using any protective circuitries.

4.2. Balanced power sharing among the healthy VSIs

The second the post-fault operating condition is adopted for sharing equally the total power among the three healthy inverters, VS1H(1), VS1H(2), and VSlLt2). To realize this post-fault condition, unbalanced power sharing has to be created between the two windings {1} and {2}; hence 1/3 of the total power must be supplied by each inverter. Through Eq. 9 to Eq. 11, Eq. 15 to Eq. 16, the postfault condition can be predicted as:

7(2> :

-v(2) 2 « k2,= l,

P > = 0

{pH> = 3 P

P(2=3P k 1

1 « k = 3 pH2=—P 3

Prated =8 kW Rs =0.51 a

Is, rated = 16 Arms Rr =0.42 a

Vs,rated = 125 Vrms Ls1 =58.2 mH

grated =2n50 rad/s Lr =58.2 mH

P =2 (pairs) M1 =56 mH

For investigation purposes Eq. 19 will be formulated in numerical simulations/experimental test to represent this second postfault condition without using any protective circuitries.

5. Numerical simulation and experimental implementation results

Table 1 gives the main numerical simulation parameters of ac motor drive system. Complete six-phase (quad) asymmetrical open-end windings motor is numerically developed in PLECS/Matlab simulation software. Table 2 gives the main hardware prototype parameters of quad-inverter system. For simplicity in implementation with experimental task, tests are carried out by two DSP TMS320F2812 processor, each one controlling two three-phase inverter (VS1h(1) and VS1l(1), VS1h(2) and VS1l(2)) with two three-phase open-end impedance (R-L) load.

Fig. 5(a) provides the overall view of laboratory setup of prototype hardware modules and Fig. 5(b) shows the detailed view of control units and the whole six-phase (quad) inverter prototype hardware system. DSP-1 performs all calculations as master control unit and modulates inverters (VS1H(1) and VS1L(1)). DSP-2 receives the modulating signals from the DSP-1 acts as slave control unit and modulates inverters (VS1H(2) and VS1L(2)). Communication channel was framed between two DSPs by data cables through multi-channel buffered serial port (McBSP) and properly synchronized for transmitting/ receiving data between DSPs [33,34].

5.1. Investigation for performance in healthy condition

1n this verification test, the system is analysed in healthy state for the whole time interval [0-90 ms]. Keeping all the sharing coefficients to 1/2 as depicted in Fig. 6(a) and (b), it is ensured that the total power is equally shared among the four VS1s with balanced operation. To be noted, with the frequency set to 50 Hz, modulation indexes of VS1H(1), VS1L(1), VS1H(2), VS1L(2) are

mH(1) = mi(1) = mH(2) = mL(2) = 0.9, i.e. m(1) = m(2) = 0.9.

Fig. 6(c) and (d) illustrates the simulation and experimental results of the first-phase voltages with fundamental component and phase output currents v1(1) (windings {1} purple trace) and v1(2) (windings {2} turquoise trace). As predicted, multilevel waveforms with 9-levels appeared, since the modulation index is greater than 0.5 (Fig. 2(d)) and phase shift of 30° is observed.

Six-phase phase currents i123(1) (windings {1} purple traces) and i123(2) windings {2} (turquoise traces) are shown in Fig. 6(c) (simulation) and Fig. 6(d) (experimental). Currents are showing sinusoidal

Table 2

Hardware parameters of quad-inverter system and six-phase open-winding loads.

MOSFETs (six in parallel per switch) Vishay Siliconix SUM85N15-19

MOSFET ratings Vdss = 150V; Rds = 19mO@Vcs = 10V;

Id = 85A

Carrier frequency =2 kHz (Hardware)

DC-bus capacitance (4 banks) =12 mF

DC-bus voltage (4 in all) =52 V

Load impedance (open ends, 6 in all) =6 a

Load power factor (angle) =0.67 (48°)

Load rated current =10 A

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Fig. 5. Six-phase (quad) multiphase-multilevel drives system experimental setup: (a) working area in Lab and (b) overall view of two dsp TMS320F2812 controlled complete ac drive system.

behavior and the same amplitude with correct 30° phase angle displacements, hence proving the effectiveness of the modulation strategy in healthy condition with balanced operating conditions by numerical simulation test and confirming experimental result. But slightly six-phase currents unbalanced in amplitude could be observed with experimental results, due to imperfectly balanced impedances among six-phase.

5.2. Investigation for performance in post-fault conditions with one failed inverter

Following two investigation tests shown in Figs. 7 and 8, postfault conditions were performed with healthy state [0-30 ms] and faulty condition (red shock arrow) on inverter VSIL(1) by setting Eq. 15 (kv(1) = 1). At time instant t = 30 ms the fault on inverter VSIL(1)occurs and no further actions are taken (t=30~60 ms). Further, the two proposed post-fault (redundancy) conditions (green straight arrow) is adopted at time instant t = 60 ms with respect to the strategies

provided in sub-section 4.1 and sub-section 4.2. To be noted, the frequency set to 25 Hz, modulation indexes of VSIH(1), VSIL(1), VSIH(2), VSIl(2) are mH(1) = mL(1) = mH2) = mL2) = 0.32 i.e. m(1) = m(2) = 0.32.

5.2.1. Balanced power sharing between the two open-end windings

First post-fault condition was conducted to prove the effectiveness of control strategy proposed in sub-section 4.1. Fig. 7(a) and (b) shows the numerical simulation and experimental waveforms variation of voltage and current sharing coefficients when the fault occurs (t = 30 ms, kv(1) turns to 1) and post-fault strategy (redundancy) is applied (t = 60 ms, kv(2) turns to 1) according to Eq. 17 and Eq. 18. The current sharing coefficient is set at k = 1/2 and remains unchanged.

Fig. 7(c) and (d) shows the numerical simulation and experimental waveforms of artificial line-to-neutral voltages with fundamental component of the first-phase of VSIH(1), VSIL(1) (green, red traces) and VSIH(2), VSIL(2) (gray, orange traces) respectively. When the VSIL(1) fault occurs on it (kv(1) = 1 at t = 30 ms), the output voltage

Fig. 6. (a) Simulated and (b) hardware generated waveforms (Healthy condition) of the proposed three degrees of freedom, voltage (turquoise, cyan traces) [0.25 units/ div], current sharing coefficients (blue trace) [1 units/div]. First-phase output voltages with time scaled average components and three-phase currents of open-end two windings {1} (i123(1) - purple traces), {2} (i123(1) - turquoise traces), (c) simulated [100 V/div, 10 A/div], (d) hardware [45 V/div, 10 A/div] generated waveforms.

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Fig. 7. (a) Simulated and (b) hardware generated waveforms (Post-fault condition-I) of the proposed three degrees of freedom, voltage (turquoise, cyan traces) [0.25 units/ div], current sharing coefficients (blue trace) [1 units/div]. Artificial first-phase output voltages along with time scaled average components of VS1s, open-winding {1} (VS1h(1) - green, VS1l(1) - red traces) and {2} (VS1h(2) - gray, VS1l(1) - yellow), (c) simulated [100 V/div], (d) hardware [45 V/div] generated waveforms. First-phase output voltages with time scaled average components and three-phase currents of open-end two windings {1} (i123(1) - purple traces), {2} (i123(1) - turquoise traces), (e) simulated [100 V/ div, 10 A/div], (f) hardware [45 V/div, 2 A/div] generated waveforms.

vL1(1) goes to zero, whereas for the voltage on the other side of three-phase windings {1} provided by the inverter VSIH(1), its output voltage vH1(1) doubles its value for balancing windings voltage. It is observed during this condition voltages vH2(2) and vL2(2) on windings {2} are unaffected. During faulty instant modulation indexes of VSIH(1), VSIl(1), VSIh(2), VSIl(2) are mH1 = 0.64, mim = 0, mn(2) = mi(2) = 0.32, i.e. m(1) = m(2) = 0.32. Next, the first post-fault control (redundancy) strategy is applied, the VSIL(2) turned-off (kv(2) = 1 att = 60 ms), the output voltage vL2(2) goes to zero, whereas for the voltage on the other side of three-phase windings {2} provided by the VSIH(2), its output voltage vH2(2) doubles its value for the balancing windings voltage. Now, the remaining active VSIH(1) and VSIH(2) provide the voltages vH1(1) and vH2(2) with same amplitudes and the proper 30° phase angle shift is observed. During this post-fault strategy modulation indexes of VSIh(1), VSIl(1), VSIh(2), VSIl(2) are mH1 = 0.64, = 0, mH2) = 0.64, mé2) = 0, i.e. m( 1) = m(2) = 0.32.

Fig. 7(e) and (f) illustrates the numerical simulation and experimental results of the first-phase voltages with fundamental component and phase output currents, v1(1) (purple trace) and v1(2) (turquoise trace). As predicted, multilevel waveforms reduced from

9-levels to 5-levels appeared, since the modulation index lesser than 0.5 (Fig. 2(e)) and phase shift of 30° is observed.

Six-phase phase currents i123(1) (windings {1} purple traces) and i123(2) (windings {2} turquoise traces) are shown in Fig. 7(e) (simulation) and Fig. 7(f) (experimental). It is expected that practically both voltages and currents are unaffected by the fault and transients by the power sharing. It is verified from both simulation and experimental results that the total power is equally shared between inverters VS1H(1) and VS1H(2) in this first post-fault control strategy according to Eq. 18.

5.2.2. Balanced power sharing among the three healthy VSIs

Second post-fault condition was conducted to prove the effectiveness of the proposed control strategy in sub-section 4.2. Fig. 8(a) and (b) shows the numerical simulation and experimental waveforms variation of voltage and current sharing coefficients when the fault occurs (t = 30 ms, fcv(1) turns to 1) and post-fault strategy (redundancy) is applied (t = 60 ms, k turns to 1/3) according to Eq. 19 and Eq. 20. The current sharing coefficient set at kv(2) = 1/2 and remains unchanged.

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Fig. 8. (a) Simulated and (b) hardware generated waveforms (Post-fault condition-II) of the proposed three degrees of freedom, voltage (turquoise, cyan traces) [0.25 units/ div], current sharing coefficients (blue trace) [1 units/div]. Artificial first-phase output voltages along with time scaled average components of VSIs, open-winding {1} (VS1h(1) - green, VS1l(1) - red traces) and {2} (VS1h(2) - gray, VS1l(1) - yellow), (c) simulated [100 V/div], (d) hardware [45 V/div] generated waveforms. First-phase output voltages with time scaled average components and three-phase currents of open-end two windings {1} (i123(1) - purple traces), {2} (i123(1) - turquoise traces), (e) simulated [100 V/ div, 10 A/div], (f) hardware [45 V/div, 2 A/div] generated waveforms.

Fig. 8(c) and (d) shows the numerical simulation and experimental waveforms of artificial line-to-neutral voltages with fundamental component of the first-phase of VSIH(1), VSIL(1) (green, red traces) and VS1H(2), VS1L(2) (gray, orange traces) respectively. When the VS1L(1) fault occurs on it (fcv(1) = 1 at t = 30 ms), the output voltage vL1(1) goes to zero, whereas for the voltage on the other side of three-phase windings {1} provided by the inverter VS1H(1), its output voltage vH1(1) doubles its value for balancing windings voltage. 1t is observed during this condition that voltages vH2(2) and vL2(2) on windings {2} are unaffected. During faulty instant modulation indexes of VS1H(1), VS1l(1), VS1h(2), VS1l(2) are mH(1) = 0.64, mt(1) = 0, mH2 = mL(2) = 0.32, i.e. m( 11 = m(2) = 0.32. Next, the second post-fault control ( redundancy) strategy is applied (fcf = 1/3 at t = 60 ms), active VS1h(1), VS1h(2), VS1L(2) provide the voltages with same amplitudes and the proper 30° phase angle shift is observed. During this second post-fault condition modulation indexes VS1h(1), VS1l(1), VS1h(2), VS1l(2)) are mfl(1) = mi(1) = mj/2) = 0.32, mL(1) = 0, i.e. m(1) = 0.16, m(2) = 0.32.1t is verified from both simulation and experimental results that the VS1H(1), VS1H(2), VS1H(1) provides the same power (voltages) observed from their individual fundamental components of artificial

line-to-neutral voltages in this second post-fault control strategy according to Eq. 20.

Fig. 8(e) and (f) illustrates the numerical simulation and experimental results of the first-phase voltages with fundamental component and phase output currents, v1(1) (purple trace) and v1(2) (turquoise trace). As predicted, multilevel waveforms reduced from 9-levels to 5-levels appeared, since the modulation index lesser than 0.5 (Fig. 2(e)) and phase shift of 30° is observed.

Six-phase phase currents i123(1) (windings {1} purple traces) and i123(2) (windings {2} (turquoise traces) are shown in Fig. 8(e) (simulation) and Fig. 8(f) (experimental). The change of current sharing coefficient at t = 60 ms leads to increased currents in windings {2} and decreased currents in windings {1}, according to Eq. 9. It is expected that practically both voltages and currents are unaffected by the fault and transients by the power sharing.

6. Conclusion

This manuscript exploited the original developments of postfault original control strategies for ac drive system based on four

ARTICLE IN PRESS

S. Padmanaban et aL/Engineering Science and Technology, an International Journal ■■ (2015) I

three-phase VS1 with simplified level-shifted PWM technique. The whole six-phase (quad) inverter ac drive configuration along with control strategies are numerically implemented with PLECS/ Matlab simulation software. Experimental tasks are carried with two DSP TMS320F2812 processors, controlling four VS1s with six-phase open-winding impedances (R-L) as loads. 1n normal operation, it is confirmed that output voltage generated by the ac drive system will be multilevel stepped waveforms which are equivalent to a 3-level VS1. The total power is shared with three degrees of freedom among the four VS1s by currents and voltages to quadruple the power capabilities. Further, it is verified that in the proposed post-fault conditions (one failed inverter), the total power is reduced to half and one degree of freedom is lost. Other two degrees of freedom are effectively utilized to equally share the total power between the two three-phase open-end winding (motor/R-L impedance) loads or among the three healthy VS1s. Finally, both the obtained simulation and experimental results show close agreement with the developed theoretical predictions.

References

[1] A. Siddique, G.S. Yadava, B. Singh, A review of stator fault monitoring techniques of induction motors, IEEE Trans. Energ. Conv. 20 (1) (2005) 106-114.

[2] G.B. Kliman, W.J. Premerlani, R.A. Koegl, D. Hoeweler, Sensitive, on-line turn-to-turn fault detection in AC motor, J. Elec. Mach. Power Syst. 28 (10) (2000) 915-927.

[3] F. Blaabjerg, M.M. Pecht, Robust design and reliability of power electronics, IEEE Trans. Power Electron. 30 (5) (2015) 2373-2374.

[4] H. Wang, M. Liserre, F. Blaabjerg, P.P. de Rimmen, J.B. Jacobsen, T. Kvisgaard, et al., Transitioning to physics-of-failures as a reliability driver in power electronics, IEEE J. Emerg. Sel. Top. Power Elec. 2 (1) (2014) 97-114.

[5] S. Yang, A. Bryant, P. Mawby, D. Xiang, L. Ran, P. Tavner, An industry-based survey of reliability in power electronic converters, IEEE Trans. Ind. Electron. 47 (3) (2011)1441-1451.

[6] S. Yang, D. Xiang, A. Bryant, P. Mawby, L. Ran, P. Tavner, Condition monitoring for device reliability in power electronic converters: a review, IEEE Trans. Power Electron. 25 (11) (2010) 2734-2752.

[7] A. Bellini, F. Filippetti, C. Tassoni, G.A. Capolino, Advances in diagnostic techniques for induction machines, IEEE Trans. Ind. Electron. 55 (12) (2008) 4109-4126.

[8] F. Meinguet, P. Sandulescu, X. Kestelyn, E. Semail, A method for fault detection and isolation based on the processing of multiple diagnostic indices: application to inverter faults in AC drives, IEEE Trans. Vehic. Technol. 62 (3) (2013) 995-1009.

[9] A.L. Julian, G. Oriti, A comparison of redundant inverter topologies to improve voltage source inverter reliability, IEEE Trans. Ind. Appl. 43 (5) (2007) 13711378.

[10] I.P. Georgakopoulos, E.D. Mitronikas, A.N. Safacas, Detection of induction motor faults in inverter drives using inverter input current analysis, IEEE Trans. Ind. Electron. 58 (9) (2011) 4365-4373.

[11] E. Levi, Multiphase electric machines for variable-speed applications, IEEE Trans. Ind. Appl. 55 (5) (2008) 1893-1909.

[12] W. Cao, B.C. Mecrow, G.J. Atkinson, J.W. Bennett, D.J. Atkinson, Overview of electric motor technologies used for More Electric Aircraft (MEA), IEEE Trans. Ind. Electron. 59 (9) (2012) 3523-3531.

[13] S. Williamson, S. Smith, C. Hodge, Fault tolerance in multiphase propulsion motors, J. Mar. Eng. Technol. 3 (1) (2004) 3-7 Taylor & Francis Publications.

[14] S.K. Singh, P. Vinay, Analysis of a multiphase induction machine under fault condition in a phase-redundant A.C. drive system, J. Elec. Mach. Power Syst. 28 (6) (2000) 577-590,3-7 Taylor & Francis Publications.

[15] A. Tani, M. Mengoni, L. Zarri, G. Serra, D. Casadei, Control of multi-phase induction motors with an odd number of phases under open circuit faults, 1EEE Trans. Power Electron. 27 (2) (2012) 565-577.

[16] J. Rodriguez, S. Bernet, B. Wu, J.O. Pontt, S. Kouro, Multilevel voltage-source-converter topologies for industrial medium-voltage drives, 1EEE Trans. 1nd. Electron. 54 (6) (2007) 2930-2945.

[17] L.G. Franquelo, J. Rodriguez, J.I. Leon, S. Kouro, R. Portillo, M.M. Prats, The age of multilevel converters arrives, 1EEE 1nd. Electron. Mag. 2 (2) (2008) 28-39.

[18] L. Alberti, N. Bianchi, Experimental tests of dual three-phase induction motor under faulty operating condition, 1EEE Trans. 1nd. Electron. 59 (5) (2012) 2041-2048.

[19] R.L.A. Ribeiro, C.B. Jacobina, E.R.C. da Silva, A.M.N. Lima, Fault-tolerant voltage-fed PWM inverter ac motor drive systems, 1EEE Trans. 1nd. Electron. 51 (2) (2004) 439-446.

[20] Y. Zhao, T.A. Lipo, Space vector PWM control of dual three-phase induction machine using vector space decomposition, 1EEE Trans. 1nd. Electron. 31 (5) (1995)1100-1109.

[21] G. Grandi, A. Tani, G. Serra, Space vector modulation of six-phase VS1 based on three-phase decomposition, Proc. 1EEE 19th Symposium on Power Electronics, Electrical Drives etc., SPEEDAM'08, Taormina (1T), 674-679, 2008.

[22] G. Grandi, C. Rossi, A. Lega, D. Casadei, Multilevel operation and input power balancing for a dual two-level inverter with insulated dc sources, 1EEE Trans. 1nd. Appl. 44 (6) (2008) 1815-1824.

[23] R. Kanchan, P. Tekwani, K. Gopakumar, Three-level inverter scheme with common mode voltage elimination and dc link capacitor voltage balancing for an open-end winding induction motor drive, 1EEE Trans. Power Electron. 21 (6) (2006) 676-683.

[24] J. Kim, J. Jung, K. Nam, Dual-inverter control strategy for high-speed operation of EV induction motors, 1EEE Trans. 1nd. Electron. 51 (2) (2004) 312-320.

[25] P. Sanjeevikumar, G. Grandi, F. Blaabjerg, J.O. Ojo, P.W. Wheeler, Power sharing algorithm for vector controlled six-phase AC motor with four customary three-phase voltage source inverter drive, in the engineering science and technology, Eng. Sci. Technol. 1nt. J. (2015) doi:10.1016/j.jestch.2015.02.002 Elsevier Journal Publications.

[26] G. Grandi, P. Sanjeevikumar, Y. Gritli, F. Filippetti, Fault-tolerant control strategies for quad-inverter induction motor drives with one failed inverter, Proceeding 20th 1EEE 1nternational Conference on Electrical Machines, 1CEM'12, Marseille (France), 957-964, 2012.

[27] A. 1qbal, G.K. Singh, P. Vinay, Steady-state modeling and analysis of six-phase synchronous motor, J. Syst. Sci. Cont. Eng. 2 (1) (2014) 236-249 Taylor & Francis Publications.

[28] R. Bojoi, A. Tenconi, F. Farina, F. Profumo, Dual-source fed multi-phase induction motor drive for fuel cell vehicles: topology and control, Proc. of 36th Power Electronics Specialists Conference, PESC'05, Recife, Brazil, 2676-2683, 2005.

[29] D.G. Holmes, T.A. Lipo, Pulse Width Modulation for Power Converters: Principles and Practice, 1EEE Press-John Wiley, 2003, pp. 467-469.

[30] M.V. Aware, Six-phase inverter operation with space vector pulse-width modulation for a symmetrical single neutral load, J. Electr. Power Compon. Syst. 41 (16) (2013) 1635-1653 Taylor & Francis Publications.

[31] K. Marouani, L. Baghli, D. Hadiouche, A. Kheloui, A. Rezzoug, A new PWM strategy based on a 24-sector vector space decomposition for a six-phase VS1-fed dual stator induction motor, 1EEE Trans. 1nd. Electron. 55 (5) (2008) 1910-1920.

[32] G. Grandi, C. Rossi, D. Ostojic, D. Casadei, A new multilevel conversion structure for grid-connected PV applications, 1EEE Trans. 1nd. Electron. 56 (11) (2009) 4416-4426.

[33] G. Grandi, P. Sanjeevikumar, D. Casadei, Preliminary hardware implementation of a six-phase quad-inverter induction motor drive, Proc. of European Power Electronics and Applications Conference, EPE'11, Birmingham (UK), 1-9, 2011.

[34] G. Grandi, P. Sanjeevikumar, Y. Gritli, F. Filippetti, Experimental investigation of fault-tolerant control strategies for quad-inverter converters, in: Conf. Proc. 1EEE 1ntl. Conf. on Electrical System for Aircraft, Railway and Ship Propulsion, 1EEE-ESARS'12, Bologna (1taly), 1-8, 2012.